The emitter circuit of Q1 is somewhat inductive (due its finite ft and base resistance). Consequently, the effective value of R2 in- creases with frequency. This would result in an increase in the stabilized output amplitude at high frequencies, but for the ad- dition of C3, determined experimentally to be 15 pF for the 2N3904 for maximum response flatness. Alternatively, a faster transistor can be used here to reduce HF peaking. Figure 16 shows the ac response at the stabilized output level of about
1.3V rms. Figure 17 demonstrates the output stabilization for sine wave inputs of 1 mV to 1 V rms at frequencies of 100 kHz, 1 MHz and 10 MHz
OUTPUT CHANGE – dB | 3dB |
AGC |
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0.1110100
FREQUENCY – MHz
Figure 16. AC Response at the Stabilized Output Level of 1.3 V RMS
dB | +0.2 |
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– |
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OUTPUT |
| 1M | Hz |
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| 100k | Hz |
RELATIVE | 0 |
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| 10MHz | ||
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0.001 | 0.01 | 0.1 | 1 |
INPUT AMPLITUDE – Volts RMS
Figure 17. Output Stabilization vs. RMS Input for Sine Wave Inputs at 100 kHz, 1 MHz, and 10 MHz
While the “bandgap” principle used here sets the output ampli- tude to 1.2 V (for the square wave case), the stabilization point can be set to any higher amplitude, up to the maximum output of ± (VS – 2) V which the AD600 can support. It is only neces- sary to split R2 into two components of appropriate ratio whose parallel sum remains close to the
AD600/AD602
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| +5V |
| AD590 | 300∝A |
| (at 300K) | |
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TO AD600 PIN 16 |
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C2 |
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1∝F |
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| Q1 |
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| 2N3904 |
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| R2B |
C3 | R2A VPTAT R2 = R2A R2B ≈ 806Ω | |
15pF |
TO AD600 PIN 11 | RF | |
OUTPUT | ||
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Figure 18. Modification in Detector to Raise Output to 2 V RMS
AWide Range,
Monolithic
50 dB. More troublesome is that the bandwidth is roughly pro- portional to the signal level; for example, the AD636 provides a 3 dB bandwidth of 900 kHz for an input of 100 mV rms, but has a bandwidth of only 100 kHz for a 10 mV rms input. Its logarithmic output is unbuffered, uncalibrated and not stable over temperature; considerable support circuitry, including at least two adjustments and a special high TC resistor, is required to provide a useful output.
All of these problems can be eliminated using an AD636 as merely the detector element in an AGC loop, in which the differ- ence between the rms output of the amplifier and a fixed dc ref- erence are nulled in a loop integrator. The dynamic range and the accuracy with which the signal can be determined are now entirely dependent on the amplifier used in the AGC system. Since the input to the
V | = V | log 10 | VIN (RMS ) | (4) |
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OUT | SCALE |
| VREF | |
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Figure 19 shows a practical wide dynamic range
1 V rms input. In terms of Equation 4, VREF is 10 mV and VSCALE is 2 V.
REV. A |
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